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Ordering number: EN 4037C
Monolithic Linear IC
LA7577N Super-split PLL-II VIF and SIF IF Signal Processor for TV/VTRs
Overview
The LA7577N is a high tone quality and high picture quality, video IF and sound IF IC. It employs split processing of the video IF signal and sound IF signal using SAW filters and a PLL detector. Further, the PLL detector incorporates a buzz canceler for Nyquist buzz interference suppression to achieve high tone quality.
Features
* Employs split processing for wide bandwidth video characteristics * PLL detector with buzz canceler for excellent buzz and buzz beat characteristics * APC time constant switch built-in * High-speed AGC supports double time constant method * SIF carrier level AGC in the 1st SIF stage for good SIF weak electric field characteristics * Good differential gain and phase characteristics * RF AGC easily adjusted using a variable resistor
Functions
VIF stage
* * * * * * * * * * * *
VIF amplifier PLL detector B/W noise canceler RF AGC VCO Equalizer amplifier AFT APC detector APC filter Lock detector IF AGC Buzz canceler
Package Dimensions
unit: mm
3067-DIP24S
[LA7577N]
1st SIF stage
* Preamplifier with AGC * 1st SIF detector
SIF stage
* SIF limiter amplifier * FM quadrature detector
Mute stage
* Sound mute (pin 2) * AV mute (pin 4) * IS-15 switch (pin 13)
Specifications
Absolute Maximum Ratings at Ta = 25C
Parameter Maximum supply voltage Allowable power dissipation Symbol VCC max Pd max V3, V13 Circuit voltages V11 V23 Ta 50C Conditions Ratings 13.8 1200 VCC VCC VCC Unit V mW V V V
SANYO Electric Co., Ltd. Semiconductor Business Headquarters
TOKYO OFFICE Tokyo Bldg., 1-10, 1 Chome, Ueno, Taito-ku, TOKYO, 110 JAPAN
60597HA(ID) / 11795TH(ID) No. 4037--1/16
LA7577N
Parameter
Symbol I1 I17
Conditions
Ratings -1 -10 -3 -2 3
Unit mA mA mA mA mA C C
Circuit currents1
I21 I22 I10 VCC = 9V, Ta = -20 to +75C
Operating temperature range Storage temperature range
Topg Tstg
-20 to +70 -55 to +150
1. Current flowing into the IC is positive and current flowing out is negative.
Recommended Operating Conditions at Ta = 25C
Parameter Supply voltage Operating supply voltage range Symbol VCC VCC op Ratings 9 or 12 8.2 to 13.2 Unit V V
Electrical Characteristics at Ta = 25C, VCC = 12V
Parameter [VIF] Circuit current Quiescent video output voltage Maximum RF AGC voltage Minimum RF AGC voltage Quiescent AFT voltage Input sensitivity AGC dynamic range Maximum allowable input Video output amplitude Output signal-to-noise ratio Sync signal tip voltage 920kHz beat level Frequency characteristic Differential gain Differential phase Maximum AFT voltage Minimum AFT voltage White-noise threshold voltage White-noise clamp voltage Black-noise threshold voltage Black-noise clamp voltage AFT detector sensitivity VIF-stage input resistance VIF-stage input capacitance APC pull-in range (U) APC pull-in range (L) VCO maximum variation range I9 V21 V10H V10L V14 Vi GR Vi max Vo (video) S/N V21 (tip) l920 fC DG DP V14H V14L VWTH VWCL VBTH VBCL Sf Ri (VIF) Ci (VIF) fPU-2 fPL-2 fU fL V18 = 3V V18 = 7V f = 58.75MHz f = 58.75MHz Vi = 10mV P = 0, C = -4dB, S = -14dB P = 0, S = -14dB Vi = 10mV, 87.5% mod, fP = 58.75MHz V13 = 5V V13 = 5V V13 = 7V V13 = 7V V13 = 5V 44 6.6 10.6 - 3.0 33 59 100 1.95 49 4.15 37 6 - - 11 0 8.9 5.3 3.4 5.3 44 0.8 - 0.6 - 0.6 - 55 7 11 0 5.9 39 65 105 2.25 55 4.45 43 8 3 2 11.5 0.4 9.3 5.7 3.7 5.7 60 1.3 3.0 1.6 -1.6 1.6 -1.6 68 7.4 11.4 0.5 8.0 45 - - 2.55 - 4.75 - - 6 5 12 1.0 9.7 6.1 4.0 6.1 84 1.75 6.0 - -0.8 - -0.8 mA V V V V dB/V dB dB/V Vp-p dB V dB MHz % deg V V V V V V mV/kHz k pF MHz MHz MHz MHz Symbol Conditions min typ max Unit
No. 4037--2/16
LA7577N
Parameter VCO control sensitivity [1st SIF] 4.5MHz conversion gain 4.5MHz output level 1st SIF stage maximum input 1st SIF stage input resistance 1st SIF stage input capacitance [SIF] SIF limiting sensitivity FM detector output voltage AM rejection Total harmonic distortion SIF signal-to-noise ratio [Mute, Defeat] AFT defeat start voltage AV mute threshold FM mute threshold AFT defeat voltage
Symbol
Conditions V18 = 4.6 to 5V
min 1.5
typ 3.1
max 6.2
Unit kHz/mV
VG VSIF1 VSIF max Ri (SIF1) Ci (SIF1) Vi = 10mVrms +2.2dB, -1dB f = 54.25MHz f = 54.25MHz
21 50 60 1.2 -
26 75 70 2 3
31 110 2.7 6
dB mVrms mVrms k pF
Vi (lim) Vo AMR THD S/N (SIF)
V13 = 5V V13 = 5V V13 = 5V V13 = 5V V13 = 5V
- 400 40 - 60
33 600 49 0.5 78
39 790 - 1.0 -
dB/V mVrms dB % dB
VD11 V4TH V2TH VD14
0.5 0.5 0.5 5.4
2.3 1.9 2.0 6
- - - 6.6
V V V V
Electrical Characteristics at Ta = 25C, VCC = 9V
Parameter [VIF] Circuit current Quiescent video output voltage Maximum RF AGC voltage Minimum RF AGC voltage Quiescent AFT voltage Input sensitivity Video output amplitude Sync signal tip voltage Maximum AFT voltage Minimum AFT voltage White-noise threshold voltage White-noise clamp voltage Black-noise threshold voltage Black-noise clamp voltage AFT detector sensitivity [SIF] FM detector output voltage [Mute, Defeat] AFT defeat start voltage AV mute threshold FM mute threshold AFT defeat voltage VD11 V4TH V2TH VD14 0.5 0.5 0.5 3.9 1.6 1.1 1.9 4.5 - - - 5.1 V V V V Vo V13 = 5V 400 600 790 mVrms I9 V21 V10H V10L V14 Vi Vo (video) V21 (tip) V14H V14L VWTH VWCL VBTH VBCL Sf Vi = 10mV V13 = 5V V13 = 5V V13 = 7V V13 = 7V V13 = 5V 39 5.0 7.6 - 2.6 37 1.5 3.25 8 - 6.8 4.0 2.5 2.5 28 48 5.4 8 0 4.5 43 1.75 3.55 8.5 0.3 7.2 4.4 2.8 4.1 39 59 5.8 8.4 0.5 6.0 49 2.0 3.85 9.0 1.0 7.6 4.8 3.1 4.5 55 mA V V V V dB/V Vp-p V V V V V V V mV/kHz Symbol Conditions min typ max Unit
No. 4037--3/16
LA7577N
Sample Application Circuit (Japan)
No. 4037--4/16
LA7577N
Sample Application Circuit (Japan)
(when the SIF, 1st SIF, AFT and RF AGC are not used)
When the SIF stage is not used
* Leave pin 1 open * Tie pin 2 to GND * Leave pin 24 open
When the 1st SIF stage is not used
* Connect a 0.01F capacitor between pin 8 and GND (leave the 0.01F capacitor on pin 23 connected to GND) * Leave pin 22 open
When the AFT circuit is not used
* Tie pins 11 and 12 to GND * Leave pin 14 open
When the RF AGC circuit is not used
* Connect a 0.01F capacitor between pin 4 and GND * Leave pin 10 open
No. 4037--5/16
LA7577N
LA7577N Interface Circuit
No. 4037--6/16
LA7577N
Buzz Canceler
Phase-locked loop (PLL) detectors feature lower harmonic distortion in the video stage, higher IF phase differential suppression and much lower audio buzz than conventional quasi-synchronous detectors. However, voltage-controlled oscillators (VCO) in PLL detectors, generally, are highly susceptible to interference from flyback pulses. This interference can affect the frequency of the VCO, resulting in added output noise components and audio buzz. This interference is minimized by VCO supply voltage regulation. The PLL detector is shown in Figure 1. The automatic phase control (APC) circuit multiplies the IF signal by the VCO output signal, which is phase shifted by 90, to suppress the AM component. The APC output is passed through a low-pass filter to form the VCO control signal. This results in a signal with a good carrier-to-noise ratio (C/N).
Figure 1. PLL detector A simple PLL detector, however, can cause other audio problems, because the broadcast signal is transmitted using vestigial sideband modulation. In this case, the RF signal is converted to an IF signal by the Nyquist slope of the SAW filter. Since the sidebands in the vicinity of the picture carrier are attenuated, the magnitudes of the upper and lower sideband vectors are different. The result is a phase distortion component, ,in the composite vector as shown in Figure 2.
Figure 2. Phase noise component
No. 4037--7/16
LA7577N
This phase distortion is the cause of audio buzz, or Nyquist buzz, because the VCO synchronizes to the composite vector. A Nyquist buzz cancelation circuit is incorporated into the LA7577N to reduce the level of this noise as shown in Figure 3.
Figure 3. PLL detector with buzz cancelation A typical signal with Nyquist buzz is shown in Figure 4 together with the compensating signal generated by the Nyquist-slope canceler and the resultant signal. The circuit shown in Figure 3 is highly effective in suppressing audio buzz caused by the 4.5MHz IF beat signal in Japanese multiplexed (L - R) audio or American (MTS) Multichannel TV Sound (L - R) signals. As buzz cancelation is independent of the PLL loop time constant, other parameters such as automatic phase control can be optimized to eliminate interference from flyback pulses. Figure 4. Nyquist buzz cancelation waveforms
Design Notes
FM Detector Output (Pin 1)
The FM detector output is an emitter follower with a 200 series protection resistor as shown in Figure 5. In multiplex audio applications where pin 1 is connected to the input of a multiplexed audio decoder, the input resistance of the decoder can decrease, causing distortion of the (L - R) signal. In this case, a 5.1k or larger resistor, R1, should be connected between pin 1 and ground. In monophonic applications, an RC de-emphasis circuit should be connected as shown in Figure 6. The time constant is given by R2 x C.
Figure 6. RC de-emphasis circuit
Figure 5. FM detector output
No. 4037--8/16
LA7577N Typical AGC filter time constants
Pin Component C1 3 R1 C2 C3 13 R2 820k 820k 820k Single time constant 330pF - - 0.47F Double time constant 330pF 2.2k 0.47F 0.068F 330pF 1.8k 0.1F 0.047F
FM Discriminator (Pin 2)
The quadrature detector frequency at which the 90 phase shift occurs is determined by the tuned circuit connected to pin 2 as shown in Figure 7. The detector bandwidth characteristics are determined largely by the coil Q and damping resistance. The damping resistor should be chosen for the desired output level and bandwidth characteristics. FM muting is achieved by holding point A, in Figure 7, at 1V DC.
Mute switch (IS-15 switch) The black-noise canceler can be disabled by pulling pin 13 to 1V or lower. An external AGC source can then be applied to pin 3 to drive the AGC circuit. This mode of operation is designed for use with an IS-15 (EIA standard) switch. Ghosting problems Reflected signals which have a phase different from that of the main signal can cause distortion of the horizontal sync pulse, as shown in Figure 9. As a result, the same chargeto-discharge current ratio of the IF AGC cannot be maintained. If the phase difference is large, the video signal can also be distorted as shown in Figure 10. Distortion can be minimized by connecting a 820k to 1M resistor between pin 13 and ground.
Figure 7. FM discriminator
IF AGC (Pins 3 and 13)
The IF signal is peak detected and averaged by the filters connected to pins 13 and 3, which are the 1st AGC and 2nd AGC, respectively, as shown in Figure 8. The IF AGC audio component of the input signal to the video IF stage is first removed by an audio trap.
Figure 9. Horizontal sync pulse distortion
Figure 10. Video signal distortion
Figure 8. IF AGC circuits
No. 4037--9/16
LA7577N
RF AGC Variable Resistor (Pin 4)
The operating point of the RF AGC can be adjusted using a variable resistor connected to pin 4 as shown in Figure 11. When pin 4 is pulled to 0.5V or lower, both the FM and video outputs are muted.
Figure 13. 1st SIF stage
Figure 11. RF AGC adjustment
VIF Input (Pins 5 and 6)
The VIF amplifier inputs on pins 5 and 6 should be capacitively coupled to block DC. The input signal is the average of the signals on these inputs. The input resistance is approximately 1.5k and the input capacitance is approximately 3pF. Figure 14. SAW filter matching
RF AGC Output (Pin 10)
The RF AGC output on pin 10 is an emitter follower with a 200 series protection resistor as shown in Figure 15. The value of the bleeder resistor connected between pin 10 and the tuner, shown in Figure 16, should be chosen based on the tuner maximum gain.
Figure 12. VIF stage
Figure 15. RF AGC output
1st SIF Input (Pin 8)
The 1st SIF amplifier input on pin 8, shown in Figure 13, should be capacitively coupled to block DC. If a SAW filter is used, an inductor should also be connected as shown in Figure 14. This matches the SAW filter output capacitance to the LA7577N input capacitance and increases the sensitivity. The inductor typically would be 0.62H (for Japan), 1.0H (for the USA) or 1.3H (for PAL countries).
Figure 16. Bleeder resistor connection
No. 4037--10/16
LA7577N
AFT Tank (Pins 11 and 12)
The automatic frequency tuner (AFT) tank connected to pins 11 and 12 generates the 90 phase shift required for quadrature detection. The band-pass frequency characteristics of the IF SAW filter and the AFT tank are shown in Figure 17(A) and 17(B), respectively. The combined response is shown in Figure 17(C). The resulting extended low-frequency response, which increases susceptibility to incorrect operation, can be reduced by connecting capacitor C2 in series with the AFT tank as shown in Figure 18. The resultant frequency response is shown in Figure 17(D). Capacitors C1 and C2 should have a ratio of approximately 5 to 1. An inductor or resistor should also be connected in parallel with C2 to maintain the DC balance of the AFT tank. The AFT can be defeated by connecting pin 11 to ground through resistor R1, which should be 20k or lower.
Figure 18. AFT tank
AFT Output (Pin 14)
An external bleeder resistor is required to generate the AFT voltage. The AFT loop time constant is formed by external resistor R3 and capacitor C2, as shown in Figure 19. The resistor also provides overvoltage protection. Fluctuations in the AFT quiescent output voltage, if present in station selector systems using PLLs or voltage synthesizers, can be reduced by connecting series resistor R4 as shown in Figure 20. Note, however, that this also reduces the AFT range.
Figure 17. AFT tank characteristics
Figure 19. AFT loop time constant
No. 4037--11/16
LA7577N
Composite Video Output (Pin 17)
The 4.5MHz composite video output circuit is shown in Figure 22. A resistor should be connected between this emitter-follower output and ground to ensure adequate output drive capability. The resistor should be 1.2k (VCC = 12V), or 1k (VCC = 9V).
Figure 20. AFT output
VCO Tank (Pins 15 and 16)
The VCO tank circuit is shown in Figure 21. The tank circuit capacitors connected between pins 15 and 16 should be in the range 20 to 27pF (24pF is recommended). The VCO tank susceptibility to external effects can be reduced by using either chip capacitors or capacitors integrated with the tank coil. Figure 22. Composite video output
APC Filter (Pin 18)
Time-constant switching is incorporated into the VCO for automatic phase control (APC). When the PLL is locked, the VCO is controlled by loop A, shown in Figure 23. When the PLL is unlocked or the signal is weak, the VCO is controlled by loop B which has higher gain. The increased APC loop gain also increases the pull-in range. The recommended range for the external APC filter resistor is 47 to 150, and for the capacitor, 0.47F.
Figure 21. VCO tank
Figure 23. APC filter
No. 4037--12/16
LA7577N
Figure 24. Equalization amplifier
Equalization Amplifier (Pins 19 to 21)
The video signal, after passing through the 4.5MHz trap, is input on pin 19 to the equalization amplifier, and output on pin 21. A resistor should be connected between the emitter-follower output and ground to ensure adequate output drive capability. The resistor should be 2.7k (VCC = 12V) or 2.2k (VCC = 9V). A buffer transistor should be used if the signal is taken off-board. Equalization amplifier design The equalization amplifier has an external series resonant circuit, shown in Figure 24, which controls the frequency characteristic. The output voltage, Vo, is given by the following equation: Vo = (R1/Z + 1) (Vi + Vin) Since the input voltage, Vin, is small, the gain is given approximately by the following equation: AV = Vo/Vi = R1/Z + 1 The amplifier can be used as a voltage amplifier by connecting a network to pin 20 as shown in Figure 25. The bleeder resistor should be chosen to avoid excessive gain and extreme video sync tip voltages.
External bleeder resistor selection If the equalization amplifier is configured for non-unity gain, bleeder resistors R2 and R3, shown in Figure 26, are required to ensure that the output DC voltage does not change. The sync tip voltage does not change if VX is approximately equal to V21. VX is given by the following equation: VX = VCC x R2/(R2 + R3) The voltage gain is given by: AV = 1 + 1000/Z1 where Z1 = R2 x R3/(R2 + R3) and resistors R2 and R3 are given by: R2 = 1000 x VCC/[(VCC - VX) x (AV - 1)] R3 = 1000 x VCC/[VX x (AV - 1)]
Figure 25. Voltage amplifier configuration
Figure 26. External bleeder resistor circuit
No. 4037--13/16
LA7577N
1st SIF Output (Pin 22)
The 1st SIF output is an emitter follower with internal 100 series resistor as shown in Figure 27. An additional series resistor should be used for impedance matching to the ceramic band-pass filter.
Figure 27. 1st SIF output Figure 29. SIF stage input circuit
1st SIF AGC Filter (Pin 23)
The 1st SIF amplifier has an AGC range of approximately 30dB. The capacitor on pin 23 is normally 0.01F, but may, depending on the situation, be as large as 4.7F (4.7F is recommended when using the filter for NICAM signal processing).
Figure 28. 1st SIF AGC filter
Figure 30. PCB layout examples
SIF Input (Pin 24)
The input impedance of the amplifier, shown in Figure 29, is approximately 1k. Any interference on pin 24, a video signal for example, can cause audio buzz or heterodyning. Good circuit board layout is essential. Examples of both good and poor layout are shown in Figure 30.
No. 4037--14/16
LA7577N
Sanyo SAW Filters
Two types of surface acoustic wave (SAW) filter built on different piezoelectric substrates can be used with the LA7577N--Lithium Tantalate and Lithium Niobate. Lithium Tantalate (LiTaO3) SAW filters LiTaO3 SAW filters have a low temperature coefficient of -18ppm/C and good stability, but have high insertion loss. An external coil is required at the output for level matching as shown in Figure 31. LiTaO3 SAW filters cover the Japanese and American bands, which both have relatively high IF frequencies. These filters have part numbers of the form TSF1xxx or TSF2xxx.
Figure 31. LiTaO3 SAW filter Lithium Niobate (LiNbO3) SAW filters LiNbO3 SAW filters have a relatively high temperature coefficient of -72ppm/C, but have an insertion loss approximately 10dB lower than LiTaO3 filters. A matching circuit is, therefore, not required at the output, as shown in Figure 32. As a result of the lower insertion loss, the passband ripple is higher. However, the low impedance and low feedthrough of these filters make them less susceptible to stray capacitance effects caused by external components and PCB layout, resulting in greater stability. LiNbO3 SAW filters cover the PAL and American bands, which have relatively lower IF frequencies. These filters have part numbers of the form TSF5xxx.
Figure 32. LiNbO3 SAW filter
VCO Tank Circuit
VCO tank circuit with built-in capacitor When the IC power supply is switched ON, the heat generated by the IC is conducted by the PCB, including into the VCO tank. The tank coil legs effectively act as a heatsink and the heat is dissipated, such that an insignificant amount of heat is conducted into the VCO tank capacitor. As a result, the effect on VCO drift is made smaller. Even so, it is recommended that the inductor and capacitor be chosen so that their temperature characteristics effectively cancel. Accordingly, it is preferable to use inductors with low temperature coefficient cores and low temperature coefficient capacitors. VCO tank circuit with external capacitor If using an external capacitor, the heat generated by the IC is conducted by the PCB, including to the external capacitor. If this happens, the heat affects the capacitor and changes its capacitance value. However, because the VCO tank coil is not significantly affected, the VCO tank tuning point changes. In this case, it is highly preferable to use inductors with low temperature coefficient cores and low temperature coefficient capacitors.
No. 4037--15/16
LA7577N
Coil Specifications
Component Japan f = 58.75MHz USA f = 45.75MHz PAL countries f = 38.9MHz
VCO coil T1
6T 0.12 C = 24pF
9T 0.12 C = 24pF
11T 0.12 C = 24pF
HW6226-4
HW6227-4
MA6389
AFT coil T2
3.5T 0.5
5.5T 0.5
7.5T 0.5
MA8181
MA6343
MA7115
SIF coil T4
19T 0.08 C = 100pF
19T 0.08 C = 100pF
25T 0.08 C = 100pF
KS6102-1
KS6102-1
MA8182
VIF SAW filter (Sanyo)
TSF1132L, TSF1137U
TSF1229L, TSF1241U
TSF5315
SIF SAW filter (Sanyo)
TSB1101P
TSB1205P
-
s
No products described or contained herein are intended for use in surgical implants, life-support systems, aerospace equipment, nuclear power control systems, vehicles, disaster/crime-prevention equipment and the like, the failure of which may directly or indirectly cause injury, death or property loss. Anyone purchasing any products described or contained herein for an above-mentioned use shall: Accept full responsibility and indemnify and defend SANYO ELECTRIC CO., LTD., its affiliates, subsidiaries and distributors and all their officers and employees, jointly and severally, against any and all claims and litigation and all damages, cost and expenses associated with such use: Not impose any responsibility for any fault or negligence which may be cited in any such claim or litigation on SANYO ELECTRIC CO., LTD., its affiliates, subsidiaries and distributors or any of their officers and employees, jointly or severally. Information (including circuit diagrams and circuit parameters) herein is for example only; it is not guaranteed for volume production. SANYO believes information herein is accurate and reliable, but no guarantees are made or implied regarding its use or any infringements of intellectual property rights or other rights of third parties.
s
s
This catalog provides information as of June, 1997. Specifications and information herein are subject to change without notice.
No. 4037--16/16

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